Undersampling

Chebyshev filters are analog or digital filters having a steeper roll-off and more passband ripple (type I) or stopband ripple (type II) than Butterworth filters. Chebyshev filters have the property that they minimize the error between the idealized and the actual filter characteristic over the range of the filter,Template:Fact but with ripples in the passband. This type of filter is named after Pafnuty Chebyshev because its mathematical characteristics are derived from Chebyshev polynomials.

Because of the passband ripple inherent in Chebyshev filters, the ones that have a smoother response in the passband but a more irregular response in the stopband are preferred for some applications.

Type I Chebyshev filters

The frequency response of a fourth-order type I Chebyshev low-pass filter with $\epsilon =1$

These are the most common Chebyshev filters. The gain (or amplitude) response as a function of angular frequency $\omega$ of the nth-order low-pass filter is equal to the absolute value of the transfer function $H_n(j\omega )$:

$G_n(\omega )=|H_n(j\omega )|=\frac{1}{\sqrt{1+{\epsilon }^2{T}_n^2\left(\frac{\omega }{{\omega }_0}\right)}}$

where $\epsilon$ is the ripple factor, ${\omega }_0$ is the cutoff frequency and $T_n$ is a Chebyshev polynomial of the $n$th order.

The passband exhibits equiripple behavior, with the ripple determined by the ripple factor $\epsilon$. In the passband, the Chebyshev polynomial alternates between -1 and 1 so the filter gain will alternate between maxima at G = 1 and minima at $G=1/\sqrt{1+{\epsilon }^2}$. At the cutoff frequency ${\omega }_0$ the gain again has the value $1/\sqrt{1+{\epsilon }^2}$ but continues to drop into the stop band as the frequency increases. This behavior is shown in the diagram on the right. The common practice of defining the cutoff frequency at −3 dB is usually not applied to Chebyshev filters; instead the cutoff is taken as the point at which the gain falls to the value of the ripple for the final time.

The order of a Chebyshev filter is equal to the number of reactive components (for example, inductors) needed to realize the filter using analog electronics.

The ripple is often given in dB:

Ripple in dB = $20{\log }_{10}\sqrt{1+{\epsilon }^2}$

so that a ripple amplitude of 3 dB results from $\epsilon =1.$

An even steeper roll-off can be obtained if we allow for ripple in the stop band, by allowing zeroes on the $j\omega$-axis in the complex plane. This will however result in less suppression in the stop band. The result is called an elliptic filter, also known as Cauer filter.

Poles and zeroes

Log of the absolute value of the gain of an 8th order Chebyshev type I filter in complex frequency space (s = σ + jω) with ε = 0.1 and ${\omega }_0=1$. The white spots are poles and are arranged on an ellipse with a semi-axis of 0.3836... in σ and 1.071... in ω. The transfer function poles are those poles in the left half plane. Black corresponds to a gain of 0.05 or less, white corresponds to a gain of 20 or more.

For simplicity, assume that the cutoff frequency is equal to unity. The poles $({\omega }_{pm})$ of the gain function of the Chebyshev filter are the zeroes of the denominator of the gain function. Using the complex frequency s, these occur when:

$1+{\epsilon }^2{T}_n^2(-js)=0.$

Defining $-js=\cos (\theta )$ and using the trigonometric definition of the Chebyshev polynomials yields:

$1+{\epsilon }^2{T}_n^2(\cos (\theta ))=1+{\epsilon }^2{\cos }^2(n\theta )=0.$

Solving for $\theta$

$\theta =\frac{1}{n}\arccos \left(\frac{\pm j}{\epsilon }\right)+\frac{m\pi }{n}$

where the multiple values of the arc cosine function are made explicit using the integer index m. The poles of the Chebyshev gain function are then:

$s_{pm}=j\cos (\theta )$

$=j\cos (\frac{1}{n}\arccos \left(\frac{\pm j}{\epsilon }\right)+\frac{m\pi }{n}).$

Using the properties of the trigonometric and hyperbolic functions, this may be written in explicitly complex form:

$s_{pm}^{\pm }=\pm \sinh \left(\frac{1}{n}\mathrm{a}\mathrm{r}\mathrm{s}\mathrm{i}\mathrm{n}\mathrm{h}\left(\frac{1}{\epsilon }\right)\right)\sin ({\theta }_m)$

$+j\cosh \left(\frac{1}{n}\mathrm{a}\mathrm{r}\mathrm{s}\mathrm{i}\mathrm{n}\mathrm{h}\left(\frac{1}{\epsilon }\right)\right)\cos ({\theta }_m)$

where m = 1, 2,..., n  and

${\theta }_m=\frac{\pi }{2}\frac{2m-1}{n}.$

This may be viewed as an equation parametric in ${\theta }_n$ and it demonstrates that the poles lie on an ellipse in s-space centered at s = 0 with a real semi-axis of length $\sinh (\mathrm{a}\mathrm{r}\mathrm{s}\mathrm{i}\mathrm{n}\mathrm{h}(1/\epsilon )/n)$ and an imaginary semi-axis of length of $\cosh (\mathrm{a}\mathrm{r}\mathrm{s}\mathrm{i}\mathrm{n}\mathrm{h}(1/\epsilon )/n).$

The transfer function

The above expression yields the poles of the gain G. For each complex pole, there is another which is the complex conjugate, and for each conjugate pair there are two more that are the negatives of the pair. The transfer function must be stable, so that its poles will be those of the gain that have negative real parts and therefore lie in the left half plane of complex frequency space. The transfer function is then given by

$H(s)=\frac{1}{2^{n-1}\epsilon }\prod _{m=1}^n\frac{1}{(s-s_{pm}^{-})}$

where $s_{pm}^{-}$ are only those poles with a negative sign in front of the real term in the above equation for the poles.

The group delay

Gain and group delay of a fifth-order type I Chebyshev filter with ε = 0.5.

The group delay is defined as the derivative of the phase with respect to angular frequency and is a measure of the distortion in the signal introduced by phase differences for different frequencies.

${\tau }_g=-\frac{d}{d\omega }\arg (H(j\omega ))$

The gain and the group delay for a fifth-order type I Chebyshev filter with ε=0.5 are plotted in the graph on the left. It can be seen that there are ripples in the gain and the group delay in the passband but not in the stopband.

Type II Chebyshev filters

The frequency response of a fifth-order type II Chebyshev low-pass filter with $\epsilon =0.01$

Also known as inverse Chebyshev, this type is less common because it does not roll off as fast as type I, and requires more components. It has no ripple in the passband, but does have equiripple in the stopband. The gain is:

$G_n(\omega ,{\omega }_0)=\frac{1}{\sqrt{1+\frac{1}{{\epsilon }^2{T}_n^2({\omega }_0/\omega )}}}.$

In the stopband, the Chebyshev polynomial will oscillate between -1 and 1 so that the gain will oscillate between zero and

$\frac{1}{\sqrt{1+\frac{1}{{\epsilon }^2}}}$

and the smallest frequency at which this maximum is attained will be the cutoff frequency ${\omega }_o$. The parameter ε is thus related to the stopband attenuation γ in decibels by:

$\epsilon =\frac{1}{\sqrt{10^{0.1\gamma }-1}}.$

For a stopband attenuation of 5dB, ε = 0.6801; for an attenuation of 10dB, ε = 0.3333. The frequency f₀ = ω₀/2π is the cutoff frequency. The 3dB frequency f_H is related to f₀ by:

$f_H=\frac{f_0}{\cosh \left(\frac{1}{n}{\cosh }^{-1}\frac{1}{\epsilon }\right)}.$

Poles and zeroes

Log of the absolute value of the gain of an 8th order Chebyshev type II filter in complex frequency space (s=σ+jω) with ε = 0.1 and ${\omega }_0=1$. The white spots are poles and the black spots are zeroes. All 16 poles are shown. Each zero has multiplicity of two, and 12 zeroes are shown and four are located outside the picture, two on the positive ω axis, and two on the negative. The poles of the transfer function will be poles on the left half plane and the zeroes of the transfer function will be the zeroes, but with multiplicity 1. Black corresponds to a gain of 0.05 or less, white corresponds to a gain of 20 or more.

Again, assuming that the cutoff frequency is equal to unity, the poles $({\omega }_{pm})$ of the gain of the Chebyshev filter will be the zeroes of the denominator of the gain:

$1+{\epsilon }^2{T}_n^2(-1/j{s}_{pm})=0.$

The poles of gain of the type II Chebyshev filter will be the inverse of the poles of the type I filter:

$\frac{1}{s_{pm}^{\pm }}=\pm \sinh \left(\frac{1}{n}\mathrm{a}\mathrm{r}\mathrm{s}\mathrm{i}\mathrm{n}\mathrm{h}\left(\frac{1}{\epsilon }\right)\right)\sin ({\theta }_m)$

$+j\cosh \left(\frac{1}{n}\mathrm{a}\mathrm{r}\mathrm{s}\mathrm{i}\mathrm{n}\mathrm{h}\left(\frac{1}{\epsilon }\right)\right)\cos ({\theta }_m)$

where m = 1, 2, ..., n . The zeroes $({\omega }_{zm})$ of the type II Chebyshev filter will be the zeroes of the numerator of the gain:

${\epsilon }^2{T}_n^2(-1/j{s}_{zm})=0.$

The zeroes of the type II Chebyshev filter will thus be the inverse of the zeroes of the Chebyshev polynomial.

$1/s_{zm}=-j\cos \left(\frac{\pi }{2}\frac{2m-1}{n}\right)$

for m = 1, 2, ..., n. 

The transfer function

The transfer function will be given by the poles in the left half plane of the gain function, and will have the same zeroes but these zeroes will be single rather than double zeroes.

The group delay

Gain and group delay of a fifth-order type II Chebyshev filter with ε = 0.1.

The gain and the group delay for a fifth-order type II Chebyshev filter with ε=0.1 are plotted in the graph on the left. It can be seen that there are ripples in the gain in the stop band but not in the pass band.

Implementation

Cauer topology

A passive LC Chebyshev low-pass filter may be realized using a Cauer topology. The inductor or capacitor values of a nth-order Chebyshev prototype filter may be calculated from the following equations:

$G_0=1$

$G_1=\frac{2A_1}{\gamma }$

$G_k=\frac{4A_{k-1}{A}_k}{B_{k-1}{G}_{k-1}},k=2,3,4,\dots ,n$

$G_{n+1}=\{\begin{array}{cc}1& \text{if }n\text{ odd}\\ {\coth }^2\left(\frac{\beta }{4}\right)& \text{if }n\text{ even}\end{array}$

G₁, G_k are the capacitor or inductor element values. f_H, the 3 dB frequency is calculated with: $f_H=f_0\cosh \left(\frac{1}{n}{\cosh }^{-1}\frac{1}{\epsilon }\right)$

The coefficients A, γ, β, A_k, and B_k may be calculated from the following equations:

$\gamma =\sinh \left(\frac{\beta }{2n}\right)$

$\beta =\ln [\coth \left(\frac{R_{db}}{17.37}\right)]$

$A_k=\sin \frac{(2k-1)\pi }{2n},k=1,2,3,\dots ,n$

$B_k={\gamma }^2+{\sin }^2\left(\frac{k\pi }{n}\right),k=1,2,3,\dots ,n$

where R_dB is the passband ripple in decibels.

Low-pass filter using Cauer topology

The calculated G_k values may then be converted into shunt capacitors and series inductors as shown on the right, or they may be converted into series capacitors and shunt inductors. For example,

• C_{1 shunt} = G₁, L_{2 series} = G₂, ...

or

• L_{1 shunt} = G₁, C_{1 series} = G₂, ...

Note that when G₁ is a shunt capacitor or series inductor, G₀ corresponds to the input resistance or conductance, respectively. The same relationship holds for G_n+1 and G_n. The resulting circuit is a normalized low-pass filter. Using frequency transformations and impedance scaling, the normalized low-pass filter may be transformed into high-pass, band-pass, and band-stop filters of any desired cutoff frequency or bandwidth.

Digital

As with most analog filters, the Chebyshev may be converted to a digital (discrete-time) recursive form via the bilinear transform. However, as digital filters have a finite bandwidth, the response shape of the transformed Chebyshev will be warped. Alternatively, the Matched Z-transform method may be used, which does not warp the response.

Comparison with other linear filters

Here is an image showing the Chebyshev filters next to other common kind of filters obtained with the same number of coefficients (all filters are fifth order):

As is clear from the image, Chebyshev filters are sharper than the Butterworth filter; they are not as sharp as the elliptic one, but they show fewer ripples over the bandwidth.

See also

Filter design

• Bessel filter
• Comb filter
• Elliptic filter

Mathematics

• Chebyshev nodes
• Chebyshev polynomial

Notes

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References

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• 20 year-old Real Estate Agent Rusty from Saint-Paul, has hobbies and interests which includes monopoly, property developers in singapore and poker. Will soon undertake a contiki trip that may include going to the Lower Valley of the Omo.
  
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